=Paper=
{{Paper
|id=Vol-3039/short43
|storemode=property
|title=Highly Sensitive Hardware Methods and Means of Determining Acupuncture Points
|pdfUrl=https://ceur-ws.org/Vol-3039/short43.pdf
|volume=Vol-3039
|authors=Konstantyn Shevchenko,Aleksey Yanenko,Roman Tkachuk,Vasyl Kuz,Vasyl Kychak
|dblpUrl=https://dblp.org/rec/conf/ittap/ShevchenkoYTKK21
}}
==Highly Sensitive Hardware Methods and Means of Determining Acupuncture Points==
<pdf width="1500px">https://ceur-ws.org/Vol-3039/short43.pdf</pdf>
<pre>
Highly Sensitive Hardware Methods and Means of Determining
Acupuncture Points
Konstantin Shevchenkoa, Oleksiy Yanenkoa, Roman Tkachukb, Vasyl Kuzb, and Vasyl
Kychakc,
a
  Igor Sikorsky Kyiv Polytechnic Institute, 37, Prosp. Peremohy, Kyiv, Ukraine, 03056
b
  Ternopil Ivan Puluj National Technical University, 56, Ruska str., Ternopil, Ukraine, 46001
c
  Vinitsa National Technical University, 95, Khmelnytsky highway, Vinnytsya, Ukraine, 21021


                Abstract
                One of the problems that arises during electropuncture diagnostics is to correctly determine
                the position of acupuncture points on the human skin. Traditional methods of determining
                acupuncture points require the passage of an electric current through of the skin, which can
                affect the patient's condition. The authors have developed methods for measuring noise
                signals to determine acupuncture points using switching-modulation conversion of
                information signals, which provides high sensitivity for determining acupuncture points (AP).
                Functional schemes of devices concerning realization of algorithms are offered. The
                electrocontact method consists in use of own noise electric signals of the patient that allows
                to carry out researches without influence of external electric signals on a human body.
                Differential radiometric method for determining AP is non-contact measurement and
                comparison of microwave radiation of two parts of the patient's body. The original structures
                of devices with switching-modulation conversion of information signals provides not only
                high sensitivity, but also eliminate the influence of temperature and instability of the
                parameters of the circuit elements on the measurement result, which increases the accuracy
                of acupuncture points.

                Keywords 1
                Acupuncture points, electropuncture diagnostics, electrical resistance, thermal noise,
                commutation-modulation transformation.

1. Introduction
    When conducting microwave, laser, thermal and other types of diagnostic and therapeutic
procedures, methods are increasingly used that involve interaction with points of human acupuncture
(electropuncture diagnostics, electropuncture therapy, reflexology, etc.) [1, 2] In some cases,
electropuncture diagnostics (ED) provides a fairly high reliability of the results and can be used along
with thermographic and ultrasound examinations of patients [3]. One of the problems that arises during
ED is to correctly determine the position of acupuncture points on the human skin. The simplest
method of finding AP is to measure the electrical resistance of the skin surface. Electrical
measurements in AP confirm the minimum value of electrical resistance in relation to other areas of
the skin [4]. At the same time, traditional methods of measuring the electrical resistance of the skin
require the passage of electric current through the AP, which can change its parameters, as well as
affect the patient's condition. This is especially true for people who use pacemakers. In addition, the


ITTAP’2021: 1nd International Workshop on Information Technologies: Theoretical and Applied Problems, November 16–18, 2021,
Ternopil, Ukraine
EMAIL: autom1@meta.ua (A. 1); op291@meta.ua (A. 2); 0andryxa0@gmail.com (A. 3); vasylkuz1992@gmail.com (A. 4);
vmkychak@gmail.com (A. 5)
ORCID: 0000-0002-7222-9352 (A. 1); 0000-0001-5450-5619 (A. 2); 0000-0002-6753-2365 (A. 3); 0000-0002-6008-7203 (A. 4); 0000-
0001-7013-3261 (A. 5)
             ©️ 2021 Copyright for this paper by its authors.
             Use permitted under Creative Commons License Attribution 4.0 International (CC BY 4.0).
             CEUR Workshop Proceedings (CEUR-WS.org)
measurement result significantly depends on the temperature and humidity of the skin surface, as well
as the amount of current used in the measurements.
    The aim of the study is to create devices for determining acupuncture points that do not change the
electrical parameters of points, do not affect the patient and provide an increase in accuracy. Such
methods include radiometric thermometry and switching-modulation conversion of information
signals, which in combination provide high sensitivity and accuracy of measuring information signals,
and have virtually no effect on the object of measurement [5, 6].

2. Physical fundamentals of the measurement method
    Physical and biological bodies (dielectric or quasi-dielectric), including the human body, emit weak
noise signals. The power of such radiation is determined by Nyquist's theorem, according to which the
mean square (dispersion) of thermal noise voltage is proportional to the temperature and resistance of
the studied part of the body, on the area of which thermal noise is measured [7]:
                                            U 2  4kT fR ,                                         (1)
where k - is the Boltzmann constant; T - thermodynamic temperature; f - frequency band in which
thermal noise and radiation are measured; R - electrical resistance.
    At a body temperature of 36o C, the level of human own radiation is very small and comparable to
the level of own noise of the receiving equipment. Therefore, it is difficult to receive and analyze such
signals. The implementation of such measurement is carried out by two-input (differential)
radiometers based on the compensation, correlation, and most often the modulation method [5, 6].
    Radiometric devices allow to measure and compare weak signals of parts of the human body in a
non-contact way without disturbing the electromagnetic state of acupuncture points.
    In [8, 9, 10] variants of two-electrode measuring devices are considered, which allow to obtain a
voltage value proportional to the square of thermal noise and, accordingly, electrical resistance. The
measurements use base and measuring electrodes, which are placed at symmetrical points of the object
of study or acupuncture points. A significant limitation in the use of such a device is that you need to
know in advance the location of the AP. In addition, the measurement result depends on the
temperature of the skin, because by formula (1) the resistance and temperature affect the voltage level
of thermal noise equally, and the signal level. Removed by the electrodes is very small and comparable
to the own noise of the electronic elements of the measuring circuit of the device. As a result, even
minor changes in the parameters of the elements of the conversion channel caused by time or
temperature instability cause significant errors.

3. Electro one-contact method and means of determination of acupuncture
   points
    The authors of this work have developed a functional scheme and proposed an algorithm for its
operation, which provides a measurement result independent of changes in the temperature of the
studied area of human skin and the instability of the parameters of the electronic elements of the
measuring device.
    Figure 1 shows the functional scheme of the tool proposed by the authors to determine the points
of acupuncture.
    The device contains the following functional elements: 1, 2 - measuring electrodes; 3 - support
electrode; 4 - common ground bus; 5, 13 - controlled switches; 6,7 - band high-frequency amplifiers;
8 - multiplier, 9 - low-pass filter; 10 - video pulse amplifier; 11 - logarithmic converter; 12 - smoothing
resistor; 14, 15 - storage capacitors; 16 - voltmeter; 17 - multivibrator. Position 18 in the drawing
indicates the area of the acupuncture point, and position 19 - the human skin.
    Determining the position of the acupuncture point is as follows. A measuring electrode 1 is placed
on the skin of the examined person in the area of the desired acupuncture point. A second measuring
electrode 2 is placed outside the AP zone.
    Due to the presence of thermal fluctuations of the elementary charge carriers between the
measuring electrode 1 and the reference electrode 3 there is an electrical noise voltage. The greatest
contribution to the noise voltage is made by the high-impedance section of the electrical circuit, which
is the epidermis.
    If we ignore the resistance of the subcutaneous tissues and the resistance of the skin in contact with
the support electrode, the mean square of the voltage (dispersion) of thermal noise in this case is
determined by the Nyquist formula:
                                            U12  4kT1fR1 ,                                        (2)
where T1 - the temperature in the area of AP R1 - electrodermal resistance between electrodes 1 and
3.
    By analogy between the measuring electrode 2 and the reference electrode 3 there is an electrical
noise voltage:
                                            U 22  4kT2 fR2 ,                                      (3)
where T2 - temperature outside the zone AP; R2 - electrodermal resistance between electrodes 2 and
3.



                                             3           2     1 18 19
                                     4
                                                               5


                                                     7                      6
                                                 ~
                                                 ~             8
                                                                        ~
                                                                        ~
                                                               9        17
                                                         ~
                                                         ~          M
                                                               10

                                                               11
                                                         ln
                                                              12

                                                               13



                                                              16
                                                         V
                                                 15                     14


Figure 1: Functional diagram of the device for finding acupuncture points

    Noise voltages (2) and (3) through the controlled switch 5 are sequentially applied to the potential
inputs of the band high-frequency amplifiers 6 and 7. The switching frequency of the controlled switch
5 is set by the multivibrator 17 and selected within 1 kHz. The bandwidth of the amplifiers is chosen
in the region of high-frequency thermal fluctuations (0,5…1 MHz). This choice of parameters of the
measuring device avoids the influence of signals of man-made origin and low-frequency flicker noise.
    Electric noise voltages after amplification are multiplied, and their value, proportional to the
product of voltages is averaged by the filter 9 lower frequencies. At the output of the filter, a constant
voltage component is formed, the value of which is proportional to the value of the mean square of
the measured noise voltage.
    At the output of the low-pass filter 9 at different positions of the switch 5 is formed two values of
DC voltage:
                                   U 3  K12 S1 K 2U12 ,                                              (4)
                                   U 4  K S K2U ,
                                           2
                                           1 1
                                                     2
                                                     2                                           (5)
where K 1 - is the gain of the band high-frequency amplifiers 6 and 7; S1 - the steepness of the
multiplication transformation; K 2 - the transfer factor of the filter 9 low frequencies.
    By multiplying the output signals of amplifiers 6 and 7, their own noise components are
compensated. This is because their own noises are uncorrelated. Therefore, the product of uncorrelated
noise signals when averaging is close to zero. That is why in formula (4) and (5) there are no
components that are due to the own noise of the amplifiers.
    Thus, during the periodic operation of the switch 5, controlled by the pulses of the multivibrator
17, the output of the filter 9 forms a sequence of rectangular video pulses, the value of the amplitude
of which is determined by formula (4) and (5). The output signal of the filter after amplification is
subjected to logarithmic transformation. As a result, the output of the logarithmic converter 11 at
different positions of the switch 5 signals are formed:
                                   U5  S2 ln K3U3 ,                                             (6)
                                   U 6  S2 ln K3U 4 ,                                                (7)
where S 2 - is the steepness of the logarithmic converter 11; K3 - is the gain of the video pulse amplifier
10.
    Signals (6) and (7) through the smoothing resistor 12 are fed to the input of the second controlled
switch 13. It, like switch 5, is controlled by signals of the multivibrator 17. As a result, during periodic
synchronous operation of switches 5 and 13 pulses with amplitude (6) the storage capacitor 14, and
the pulses with amplitude (7) - on the storage capacitor 15. There is a separate accumulation of charges
by the capacitors 14 and 15.
    The smoothing resistor 12 forms with the storage capacitors 14 and 15 integrating circuits, which
from the sequence of pulses (6) and (7) emit constant voltage components:
                                     U7  K4U5  K4 S2 ln K3U3 ,                                      (8)
                                   U8  K4U 6  K4 S2 ln K3U 4 ,                                     (9)
where K 4 - is the transmission (averaging) of the integrating circuits.
   The difference between the DC voltage components (8) and (9) is measured by a voltmeter 16
                                  U 9  U 8  U 7  K 4 S2  ln K3U 4  ln K3U 3  .               (10)
   Given that the difference of logarithms is equal to the logarithm of the relation, the formula (10)
takes the form
                                                 U
                                  U 9  K 4 S2 ln 4 .                                              (11)
                                                 U3
   After substituting in (11) the values of voltage and c (5) and (4), as well as the values of dispersion
from (3) and (2), we finally obtain
                                                  TR
                                  U10  K 4 S2 ln 2 2 .                                            (12)
                                                  T1 R1
   Since the temperature in the zone AP and the temperature near this zone are almost the same, so
we can assume T2  T1 . Then the measured voltage is determined by the formula.
                                                  R
                                  U10  K 4 S2 ln 2 .                                              (13)
                                                  R1
   From formula (13) it follows that the measured electric noise voltage is proportional to the
logarithm of the ratio of resistances outside the zone AP and in the zone AP.
   To determine the position of the AP, you need to move the measuring electrode 1 in the area of the
AP at a fixed position of the measuring electrode 2.
   The maximum readings of the voltmeter indicate that the measuring electrode 1 is at the point of
acupuncture.
4. Radiometric contactless method and means of determination of
   acupuncture points
    The radiometric non-contact method and device are implemented on the basis of a two-channel
differential radiometric system for recording the difference in the values of radiation intensity in the
microwave range. To study the gradients of the electromagnetic field of biological objects, you can
use differential radiometers that measure the difference in radiation intensities from neighboring or
remote biologically active points (BAP), as well as various (for example, symmetrical) parts of a
patient’s body to compare the radiation of two patients.
    To increase the sensitivity of differential radiometers, it is reasonably to use power feedback to
small difference intensities, which provides a deep modulation. In Fig. 2, a functional diagram of a
differential radiometers positive feedback [11] is presented, which consists of two microwave antennas
X1 and X2, attached to matching elements A1 and A2 that are connected to two inputs of the
microwave switch S1.




Figure 2: Differential radiometers for recording the difference in radiation intensities

    A hybrid tee A4 is connected to the output of a microwave switch, and the matched load R1 and
the controlled attenuator A3 are connected to its inputs, too. A microwave amplifier A5, a microwave
mixer U1, an intermediate frequency amplifier (IFA) with a filter Z1, a quadratic detector U2, a low-
frequency amplifier (LFA) A7, a synchronous detector U3, and a recorder P1 are connected tandem
to the output of a hybrid tee A4.
    The switching generator G2 is connected to the control inputs of the microwave switch S1 and the
synchronous detector U3. A noise generator G1 is connected to the first input of the controlled
attenuator A3. A control unit A6 is connected to the second input, the control module of which is
connected to the output of the low-frequency amplifier A7.
    Microwave antennas X1 and X2 receive the thermal radiation from the surface of an object. The
output signals of an antenna can be represented as dispersions of random signals:
                                     U12  ST1 ,                                                 (14)
                                     U 2  ST2 ,
                                        2
                                                                                                 (15)
where S – the antennas sensitivity; Т1 and Т2 – a temperature of controlled areas of an object surface.
         The signals U1(t) and U2(t) through matching elements A1 and A2, for example, flexible
dielectric (fluoroplastic) waveguides, and the arms of the microwave switch S1 periodically arrive at
one input of a hybrid tee A4.
    The signal from the noise generator G1 is fed to the second input of the tee through the attenuator
A3, controlled by an electrical voltage of only one polarity - negative or positive one.
    Since the controlled input of the attenuator is connected through the control unit A6, which is a
rectangular voltage generator and a power amplifier that is connected to the output of the LF- amplifier
A7, the attenuator opens for a time equal to the half-period of a low-frequency voltage, which is the
envelope of the modulated microwave signal. In this case, the half-cycle of the low frequency is equal
to the half-cycle of the switching frequency of the microwave switch S1.
   In the first switching half-period, when a signal U1(t)>U2(t) is fed to the input of the microwave
switch, the attenuator A3 opens.
   Independent noise signals are summed in a hybrid tee, the sum dispersion of which can be
represented in the following way:
                                    U 42  K1 U12  K 2U 32  U 52  ,                        (16)

where К1 – the power transmission coefficient of the hybrid tee A4; К2 – the attenuator power transfer
coefficient A3; U3(t) – the noise generator G1; U5(t) –the intrinsic noise of a one-link path of a
differential radiometer, brought to the input of the amplifier A5.
    In the second switching half-cycle, the signal U2(t)<U1(t) is supplied to the input of the microwave
switch S1, the attenuator A3 is closed by a low-frequency voltage of the opposite polarity (К2=0).
Therefore, the total noise signal can be represented by the dispersion:
                                           K    .                                            (17)
                                           2       2   2
                                        U         4       1   U U 2           5


   Signals U 4  t  and U 4  t  , that create one modulated signal, are periodically fed to mixer U1. An
amplifier with a filter Z1 selects a signal of difference frequency, the spectrum of which is determined
by the passband of the filter.
   The quadratic detector U2 receives packets of noise signals of an intermediate frequency, which
can be represented as a dispersion:
                                      U        K K  K
                                              6
                                               2
                                                      3
                                                          2
                                                              1
                                                                 2
                                                                  U
                                                                     2
                                                                      1,         U U
                                                                                  2   3       5
                                                                                                        (18)

                                     U   K K U  U 
                                              2          ,            2       2                  (19)
                                              6       3       1       2       5


where К3 – a gain of the amplifier Z1 in the filter bandpass.
    The voltage of the envelope of the switching frequency with the amplitude is allocated at the output
of the quadratic detector U2:
                                     U  K 1K 3 K 4   K 2   ,                                (20)
                                                      2     2   2
                                          7                           U   1           U U 3       2

where К4 – a conversion coefficient of the quadratic detector U2.
   An alternating voltage with an amplitude U7 (t) controls the operation of an attenuator A3 and is
simultaneously rectified by a synchronous detector U3. The rectified voltage, which is fixed by a
indicator P1, can be written as follows:
                            U 8  K1 K 3 K 5 K 6 U12  U 22  K 2U 32    U12  U 22  K 2U 32  , (21)
where К5 – the gain of amplifier A7; К6 – a conversion coefficient of asynchronous detector U3;
  K1 K 3 K 5 K 6 – a resulting coefficient of a direct conversion of RS.
   The gain of the controlled attenuator A3 is proportional to the amplitude of the low-frequency
voltage U7 (t):
                                    K 2  K 7U 7 ,                                              (22)
where К7 – the gear ratio of a control unit A6.
   If a control voltage U7 (t) is expressed through the output voltage U8(t), then:
                                          K
                                    K 2  7 U 8  U 8 ,                                        (23)
                                          K6
              K
where   7 – a coefficient of the inverse transformation of a RS output voltage.
              K6
   Substituting the value a transmission coefficient К2 of the controlled attenuator A3 from expression
(23) into the expression (21), we get:
                                              
                                                   2  1
                                    U8               U 2  U 22  .                            (24)
                                          1  U 3
   Using expressions (24), (14) and (15), which take into account the temperature of controlled areas
of an object, we finally get:
                                              S
                                    U8             T1  T2  .                               (25)
                                          1  U 32
    A change in the sign of the measured temperature difference T1  T2  leads to a change in the phase
of the low-frequency voltage at the output of the A7 amplifier by 180°.
    As a result, the switching half-period changes, in which the controlled attenuator A3 opens, and
the noise signal from the generator G1 is summed not with the signal U1(t), but with the signal U2(t)
(with higher power). Thus, the operation of differential RS is not disturbed, and its indications will be
equal to:
                                            S
                                 U8             T2  T1  .                                   (26)
                                        1  U 32
    The rectified voltage can be written in the following form because when thephase of the voltage of
a switching frequency changes by 180, the polarity of a rectified voltage changes at the output of a
synchronous detector U3:
                                              S
                                 U8                T1  T2  .                                 (27)
                                          1  U 32
    Thus, the considered differential RS works consistently at any temperature ratio of the controlled
object (Т1<Т2 or Т1>Т2), and the polarity of the measured voltage determines the sign of the controlled
temperature difference. If the feedback coupling is absent in differential RS ( = 0), then the output
voltage has the form:
                                           U 9   S T1  T2  .                                 (28)
   The introduction of positive feedback (> 0) leads to the appearance of an output voltage, which is
described by expression (27), and an increase in the sensitivity of the differential radiometer by a
factor equal to:
                                             U         1
                                          8               .                                     (29)
                                             U 9 1  U 32
   If a denominator of expression (29), for example, is equal to 0,01, then the sensitivity of differential
RS will increase 100 times due to the feedback coupling.
                                                                           
   The maximum gain in sensitivity with the condition 1    U 32   0 is limited by the possibility
of auto-oscillations in the positive feedback circuit. Phase compensation chains and amplitude limiting
elements are introduced to suppress auto-oscillations in control unit A6.
    In practice, the fluctuation threshold of sensitivity of a differential radiometer can be reduced to
10 ...10–23 W/Hz by introducing feedback coupling, which corresponds to sensitivity by temperature
   –22

difference 10-4...10-5 К.
    The usage of the considered differential RS allows to study the gradients of the temperature fields
of biological objects in the range of their electromagnetic radiation and to compare the field intensities
in biological active points of these objects.

5. Conclusion
    The commutation - modulation method and means of contact and non - contact determination of
acupuncture points proposed by the authors are based on the use of anomalous values of electrical
resistance and microwave radiation from the surface of human skin in the areas of TA.
    Internal information fluctuations of electric charges which intensity is proportional to resistance
and temperature of the investigated site of a skin of the person are used as information signals.
    Algorithms for measuring noise signals and their conversion are based on the comparison of signals
at the point of acupuncture with the adjacent part of the human body and the reference point.
    The use of the proposed method and means of determining the points of acupuncture provides
complete safety when performing diagnostic procedures.
    The result of determining the location of the TA is not affected by the temperature of the studied
area of the skin, the variability of the gain of the measuring channel of the device and the change of
the conversion factors of the passive elements.
    These advantages provide an increase in the accuracy of determining the points of acupuncture
and, accordingly, increase the effectiveness of treatment.
   Scientific novelty lies in the creation of a method and devices for taking characteristics and
parameters of the human body without affecting the measurement zones, which in our case increases
the sensitivity and accuracy of determining acupuncture points.

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[3] Sitko SP, Skripnik Yu. A., Yanenko AF Hardware support of modern technologies of quantum
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[9] Kazakov MI, Skrypnyk YO, Kireev VV Device for estimating bioelectrical activity of
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